Many of the measurements are reported in decibels (dB) and are calculated by using the following formulas:
The standard unit for the gain or loss of signals is the decibel (dB). When measuring cables, the voltage out is always less than the voltage in at the other end, so the results in dB for the preceding equations are negative, although the minus sign is generally left off in discussion.
The following paragraphs provide a basic introduction to a number of important copper LAN link characteristics. Understanding this information can help ensure the proper operation of your LAN installation. Note also that some of the test parameters apply only to testing twisted-pair cable, such as Near-end Crosstalk (NEXT).
Recent cabling standards describe two groups of tests: in-channel and between-channel. The in-channel tests are all related to what takes place within a single cable jacket. The external tests relate to influences from outside that cable-under-test. The following list of test parameters is grouped along those lines, but starts with a simple grouping where frequency-based analysis is not a critical factor.
Basic Tests and Parameters Required for In-Channel Testing
These basic measurement parameters are available from a range of diagnostic and monitoring tools, primarily because they do not require much circuitry to implement.
Before qualitative frequency-based testing is possible, a link must be verified for simple pin-to-pin continuity and pairing of the wires according to a specific wiring standard. A wiremap test is used for this purpose. The specific requirements of the wiremap test are to evaluate all eight conductors (wires) in the four-pair cable for the following installation and connectivity errors. Each of the following is discussed in detail in this chapter:
- Continuity to the remote end
- Shorts between any two or more conductors
- Reversed pairs
- Split pairs
- Transposed pairs
- Any other miswiring
A wiremap test begins with a simple continuity test to ensure that each connector pin from one end of the link is connected to the corresponding pin at the far end, and is not connected to any other conductor or the shield. If the test signal does not reach the other end, the wire is open. If the DC voltage test signal crosses onto another wire because they are touching, it is shorted. Although this is enough for telephone and other low-frequency applications, simple continuity between pins from one end of the link to the other is not sufficient for typical networking applications.
A number of vendors and organizations have supplied their own pairing diagrams over the years, most of which are quickly fading into obscurity. The TIA/EIA-568-B standard describes two pairing diagrams intended for use with standard networking protocols T568A and T568B. The pairing schemes are electrically identical and differentiate only which pair is connected to specific pins in the 8-pin modular connections (see Figure 2-2 and Figure 2-3). Although the T568B arrangement is somewhat more widely installed, the standard identifies T568A as the preferred arrangement.
Figure 2-2 TIA/EIA-568-B pinout for T568A
Figure 2-3 TIA/EIA-568-B pinout for T568B
Installers are quick to learn to pair according to the wire colors marked on the jacks and punch-down blocks. Thus, mixed use of T568A and T568B components is likely to cause link faults. If a mix of components from both standard pinout arrangements is used in the same building, it is fairly certain that wiring faults will result through inattention to detail. Be sure to use the same wiring plan throughout the network.
Figure 2-4 shows how to count pin numbers on the 8-pin modular plug (RJ45).
Figure 2-4 Position of pins in the 8-pin modular RJ45 plug
The most common wiring faults are shown in Figure 2-5.
Figure 2-5 Correct pairing and common link wiring faults
The reversed-pair cable fault is perhaps the simplest wiring fault. A pair reversal occurs when a twisted pair is not connected with straight-through pin-to-pin continuity. For example, if one wire of a twisted pair was connected to pin 1 at one end and pin 2 at the other, and from pin 2 to pin 1 for the second wire (see the example in Figure 2-2), then the pair is said to be reversed. As a carry-over from telephony, this is also sometimes called a tip/ring reversal.
Pair reversals can occur at any cable connection point, although they are most common at the RJ45 plug or jack.
Using individual wires from two different twisted pairs to form a transmit or receive pair is called a split pair. Because the two wires are not twisted together as intended, the crosstalk cancellation effects are lost, and the two wire pairs usually begin acting as antennas to improperly hear the transmitted signal as noise on the receive pair. The effect is like a telephone circuit that is echoing whatever you say into the mouthpiece directly to the earpiece. If it is not very loud, you can sometimes continue, but if the echo gets too loud it disrupts the conversation. Although a link constructed this way exhibits correct pin-to-pin continuity, it causes errors in data transmission.
Split pairs occur most frequently from two causes: at punchdown blocks or at cable connectors, where not enough care was taken during cable installation or assembly; and from technicians not understanding the importance of the twisting of the wire pairs. The second problem is usually because the technician has taken the first twisted pair and used it for pins 1 and 2, the second twisted pair for pins 3 and 4, and so on. The result is shown in Figure 2-2, where the wires used to form a wire pair (3 and 6) come from two different twisted pairs. To someone not accustomed to building network cables, splitting apart a twisted pair to straddle the middle two pins might seem completely wrong.
Cable testers cannot literally test for a split pair using standard AC frequency-based tests. DC ohms tests by digital multimeters (DMMs) do not reveal split-pair problems either. There are several methods that cable testers use to infer that a split pair is present. One of the most common methods is to infer the presence of a split pair when the NEXT measurement fails badly. If a wire pair is split, or if a link is assembled with wire that is untwisted (such as ribbon cable or untwisted telephone cable), it will have a large NEXT problem. As a result, whenever a NEXT test fails with a significant margin, it is assumed that a split pair may exist.
Transposed pairs occur when a twisted pair is connected to completely different pin pairs at both ends. Contrast this with a reversed pair, where the same pair of pins is used at both ends. This issue appears when color-coded punchdown blocks (for T568A and T568B) are mixed, and two different color codes are used at different locations in a single link.
Transposed pairs also commonly occur as the result of counting pin numbers from different sides of the connector or punchdown block at either end of the cable. This results in pin 1 connecting to pin 8, pin 2 to pin 7, and so on.
The cable shown in Figure 2-2 is transposed, but in a special way. When two Ethernet hubs or switches are connected together in series (cascading them), the transmit and receive pairs must be transposed; otherwise, receive is listening to receive and transmit is talking to transmit. This special cable is often called a crossover cable, and in this specific instance, the transposition is done on purpose. Note: Gigabit Ethernet requires that the interface be capable of correcting for transposed pairs, so use of this cable type might not be evident.
An electrical signal travels at uniform speed along a wire. The parameter used to describe this property is called the Nominal Velocity of Propagation (NVP). NVP expresses the speed at which a signal travels through a cable relative to the speed of light, and is expressed as a percentage. The actual speed of the electrical signal in a LAN cable is between 60 percent and 80 percent of the speed of light in a vacuum, or roughly 20cm (eight inches) per nanosecond. Signal speed is mainly affected by the composition of the cable insulation material (its relative permittivity).
Propagation delay is a simple measurement of how long it takes for the signal to travel down the cable being tested. This is measured on a per-pair basis on twisted-pair cable because of the physical difference in pair lengths caused by the different twist rates per pair in the cable.
Propagation delay measurements are the basis of the length measurement. TIA/EIA-568-B.1 specifies in paragraph 126.96.36.199.1 that the physical length of the link shall be calculated using the pair with the shortest electrical delay. Although the cable jacket may have length markings, testers usually measure the length of the wire based on the electrical delay as measured by the TDR function. The length of individual wire pairs inside a link may all be different, and may appear to be slightly longer than the measured length of the link being tested. This apparent discrepancy results primarily from different twist rates applied to the wire pairs within the cable, which changes the overall physical length of each pair, and thus the amount of delay measured. Another reason is that wire pairs may have different insulation material, which affects the velocity of the signal on that wire pair.
The Time Domain Reflectometry (TDR) test is used not only to determine length, but also to identify the distance to link faults such as shorts and opens. Other techniques for cable length measurement, such as capacitance and DC resistance, are unable to report the distance to a short or open.
When a cable tester makes a TDR measurement, it sends a pulse signal into a wire pair and measures the amount of time required for the pulse to return on the same wire pair. When the pulse encounters a variation in impedance, such as an open, short, or poor connection, some portion of the pulse energy is reflected back to the tester. The tester measures the elapsed time between when the pulse was sent and when the reflection was received. In addition to the comparatively large echo or reflection from the end of the cable (open circuit), smaller echoes may be detected that represent impedance changes in the link due to other forms of poor connections or defects in the cable.
The size of the reflected pulse is proportional to the change in impedance. Thus, a large change in impedance, such as a short, causes a large reflection; a small impedance change, such as a poor connection, creates a smaller reflection.
If a returning echo is larger than a threshold setting (the default is typically about 15 percent of the transmitted pulse), it displays the calculated distance to the echo source. These small echoes are called anomalies and are caused by cable faults of varying severity. Most testers display more than one distance: the distance to the end of the link as well as one or two anomalies along the way. Some of the faults that cause an echo reflection include poor connections, mixed-impedance cable segments, cable stubs, crushed cable, and severe kinks or over-tight tie-wraps. Cable test tools with high sensitivity are able to show a TDR plot that allows the user to see all anomalies along the length of the link.
Length measurements depend directly on knowing the NVP of the link under test. Most cable tester configuration screens enable users to choose from a range of cable types. For the length measurement, the primary purpose of choosing the cable type is to tell the tester what the approximate NVP value is for the cable being tested. For maintenance testing, you could leave the selection set at any cable type of the same impedance value as the cables you were testing all the time—providing you understood that the length measurement was not going to be precise. It is usually sufficient to learn that the problem is "a third of the way back from the end." With that information, you then look for a connection point (punch-down block, wall jack, etc.) in that general area. Almost all problems are found either at known connection points or in the user's workspace.
The choices for cable types are prepared using NVP values obtained from published specifications for each cable manufacturer and from worst-case values published in the standards. The variation in NVP from lot-to-lot of the same cable type from a specific manufacturer can be 5 percent or more, and may reach 10 percent between different manufacturers. Therefore, if length accuracy is critical to your situation, you must determine the true NVP of each cable batch installed in your network. Verify the tester's length measurement by testing a known-length sample of the same cable you will be installing or testing that is longer than 15 meters (50 feet). All cable analysis tools have a "calibrate" function that allows you to adjust the NVP value to match this cable sample. Very simple testers with a "length" function may not.
Delay skew is calculated as the difference between the propagation delay for each of the four wire pairs. The fastest propagation delay among the four measurements is used as one extreme, and the slowest propagation delay measured is the other extreme. The difference between the two measurements becomes the delay skew. EIA/TIA-568-B permits no more than 44ns of delay skew between the fastest and slowest pairs in the cable for the Permanent Link configuration, and 50ns for the Channel Link. The high-throughput network applications such as 1000BASE-T and 10GBASE-T are most sensitive to delay skew; they also permit no more than 50ns of delay skew.
Some newer high-speed network implementations, such as 1000BASE-T, achieve very high data rates by simultaneously transmitting data on all the wire pairs of a four-pair cabling link. The encoded signal is sent simultaneously in four parts, one part on each wire pair, and all four parts must be received very close to the same time to be interpreted correctly.
One of the reasons delay skew was first included in several testing standards is because some Category 5 cables were constructed with different insulating materials around the copper conductors. This construction is referred to as heterogeneous. Homogeneous cable construction requires that all wire pairs be constructed with one and the same kind of insulating material. The insulating material has a significant influence on the NVP of the cable. There are two (then) relatively common instances of heterogeneous cables: the 2+2 cable and the 3+1 cable. In these cables the wires in two or three pairs are insulated using Teflon FEP, whereas the wires in the other pairs are insulated using a polyethylene compound. This heterogeneous construction method was used to meet the demand for category cable in view of a Teflon shortage that plagued the industry for a few years following a fire in a Teflon plant in 1995. The Teflon FEP insulated wire pairs exhibit the typical Category 5 NVP value of 69 percent, whereas the other pairs transmit the signals somewhat slower and have an NVP value that is several points lower (65 percent or 66 percent). Those 2+2 or 3+1 cables are unable to support technologies such as 1000BASE-T due to very poor delay skew performance.
Delay skew is a critical measure for 1000BASE-T, 10GBASE-T, and any other implementation where multiple pairs are used to transmit simultaneously in the same direction. The receiver PHY must realign the received bits so that despite receiving the first data from one data unit transmission on one wire pair several time-slots away from the last data from the same data transmission on another wire pair, the whole transmission is reassembled and delivered to the next higher layer as if it were received at the same time.
Basic Frequency-Based Test Parameters Related to In-Channel Testing
The following test parameters depend largely on the frequencies used to perform the measurement. As a direct consequence of this dependence, the appropriate standards specify the maximum allowed frequency step rate or separation between tested frequencies. These tests require a substantial amount of very sensitive circuitry, and are thus rarely found in network diagnostic and monitoring equipment because of the additional bulk that would be required. Advanced cable analysis tools are usually separate testers, and are used only to test cable. Most such cable analysis tools consist of two identical test units—one bearing a display and the other nearly faceless. Both units offer the same full test and measurement capabilities and are placed at either end of the link being tested.
Attenuation is signal loss or the decrease in signal amplitude over the length of a link (see Figure 2-6). The longer the cable and the higher the signal's frequency, the greater the attenuation or loss is. Therefore, be sure to measure attenuation using the highest frequencies that the cable is rated to support.
Figure 2-6 Attenuation loss
Attenuation needs to be measured only from one direction on the link (on all pairs) because attenuation of a specific wire pair is the same when measured in opposite directions.
In Figure 2-7, the signal amplitude decreases with distance to represent signal loss through attenuation and the related measurement of insertion loss.
Figure 2-7 Attenuation (and the related measurement of insertion loss) results from the resistance of the transmission medium to the transmitted signal
Attenuation is caused by a loss of electrical energy due to the resistance of the wire (converting the energy to heat), and when energy leaks through the cable's insulating material. This loss of energy (attenuation or insertion loss) is expressed in decibels (dB). Lower attenuation values are an indication of better link performance. For example, when comparing the performance of two links at a particular frequency, a link with an attenuation of 10dB (a factor of 3.16) performs better than a link with an attenuation of 20dB (a factor of 10). Link attenuation is determined by the cable's construction, length, and the frequencies of the signals sent through the link. In the 1 to 100MHz frequency range, the attenuation is dominated by the skin effect and is proportional to the square root of frequency. That is, the higher the frequency, the greater the attenuation.
The preceding discussion about attenuation assumes that the connection to the test instrument or end-user equipment and all intermediate connections in the link have a perfect impedance match. Because there is no such thing as a perfect connection, it is necessary to look at the severity of impedance discontinuities as they relate to the frequency ranges used in a local area network. Simple attenuation tends to be linear along the cable. The more cable you have, the greater the expected attenuation and that attenuation can be fairly accurately predicted because it is linear. At speeds covered by Category 5e cable (1 to 100MHz), the impedance discontinuities that result from good cable junctions have a nearly insignificant effect, and can be included in a simple attenuation measurement that ignores their contribution. At the speeds supported by Category 6 cable (1 to 250MHz), clear evidence emerges showing that these effects can be much more pronounced, and that their effect can easily reduce the performance of the link by 4 to 6dB (see Figure 2-8). Thus, TIA/EIA-568-B has changed the test parameter name from attenuation to insertion loss to include the effect of these reflections, which are separately measured as return loss.
Figure 2-8 DTX-1800 insertion loss test results example. The top line that extends only to 100MHz is the test results limit line for this Category 5e test. The irregular line below the limit line is the measured test result.
In Figure 2-8, the top curved line is the test limit for Category 5e, and does not extend beyond 100MHz because that is the highest frequency specified for Category 5e. The wavy line below it is the current test result. The vertical line at 100MHz is the cursor, which shows the current measurement result of 14.5dB at 100MHz (a margin of 6.5 dB better performance than the test limit at that frequency). Test results for frequencies above 100MHz begin showing the echo effects of impedance discontinuities in the form of varying (non-linear) test results—the wave in the line.
An impedance discontinuity on a link causes a reduction in the signal strength due to part of the energy being reflected. At the first discontinuity, a portion of the signal is reflected back toward the transmitter. The effect is compounded at the second (and each subsequent) discontinuity where an additional portion of the remaining signal is reflected backward, but part of the reflection is also reflected forward again by the first discontinuity. Multiple echo effects are created. By the time a signal has passed through several discontinuities, there is a clear drop in signal strength, and there is a growing set of echoes that both follow the original outbound signal and return to the transmission source.
The effects of the echoes are twofold. First, the effective cable length of the link is reduced because some percentage of the signal did not reach the end. The signal is not loud enough to be heard as far away as before. Second, because of echoes the receiver begins having difficulties properly sampling and decoding the signal, which results in corrupted data, and in turn results in more errors occurring on the network. This sampling or misclocking problem is called jitter. If you are curious about how much signal is reflected at a single impedance discontinuity try the following formula. Z is the symbol for impedance. The example shows the effect of connecting a 50 ohm and 75 ohm coaxial cable together, in that order (signal source, 50 ohm cable, 75 ohm cable). Twenty percent of the signal is reflected back toward the signal source at the junction of the two cables in the example. This is obviously an extreme example of an impedance discontinuity, but the problem is the same with large or small reflections on coax and twisted pair.
As mentioned, this conspicuous behavior change at higher frequencies caused TIA/EIA-568-B to stop describing this as an attenuation test and is now calling it an insertion loss test. The only real difference between the two measurements is that insertion loss acknowledges the presence of jitter and its causes.
TIA/EIA-568-B defines the formulas to calculate the allowable insertion loss for an installed twisted-pair link for both link configurations the permanent link (formerly the basic link) and the channel. In addition, TIA/EIA-568-B shows a table of allowable values for these links. The allowable values of attenuation apply to an environment at 20°C. Attenuation increases as temperature increases: typically 1.5 percent per degree Celsius for Category 3 links, 0.4 percent per degree Celsius for Category 5e links, 0.4 percent per degree Celsius from 20°C to 40°C, and 0.6 percent from 40°C to 60°C for solid conductor Category 6 links, and so on. The network technician should remember to take temperature into consideration for both installation and testing purposes. TIA/EIA-568-B specifically permits adjustment of allowable attenuation for temperature. If the intended use environment is likely to be hotter than 60°C (140°F), another type of cable should be considered.
Cable analyzers may report the worst case attenuation test result value and the frequency at which it was measured. The testers are required to use attenuation results greater than 3dB only for Pass/Fail purposes.
Return loss is a measure of reflections caused by the impedance changes at all locations along the link and is measured in decibels (dB). Mismatches predominantly occur at locations where connectors are present, but they can also occur in cable where variations in characteristic impedance along the length of the cable are present.
The main impact of return loss is not on loss of signal strength (there is some, but generally it is not that much of a problem), but rather the introduction of signal jitter. An example of jitter was shown in Figure 2-8, where these reflections caused a visible impact on the attenuation measurement at higher frequencies. Attenuation tends to be linear (smooth line) along a cable. The measurement in Figure 2-8 shows how the echoes arrived at the receiver of the tester in phase with some frequencies and out of phase with others, resulting in a wavy line. Figure 2-9 shows possible sources of return loss along a cable link.
Figure 2-9 Sources of return loss
A simplified description of this type of jitter is that the edge of a signal representing a data bit is shifted slightly in time, such that when the receiver circuit samples the signal it incorrectly classifies the signal as either a binary 1 or 0 when it should have been the other value (see Figure 2-10). This jitter can vary the leading edge of the signal presented to the decoder in the receiver, or add to or subtract from the signal amplitude, and thereby cause decoding errors. The closer to a perfect match of characteristic impedance of the cabling to the output impedance of the transmitter, and to the input impedance of the receiver, the better the return loss measurement will be. A lab test called the "eye-pattern" is typically used to evaluate the degree of jitter present in a network, and the corresponding loss of signal strength (the amount of energy that fails to transfer from the signal source to the receiver due to impedance mismatches).
Figure 2-10 Simplified illustration of sampling problems due to signal jitter
Figure 2-10 assumes that the encoding scheme is edge sensitive. When the data signal becomes misaligned with reference to the clock, sampling errors take place. In the example, probable sampling errors are shown with an X in place of the binary value.
The return loss measurement varies significantly with frequency. Any variation in characteristic impedance of the cabling is one source of return loss. Another source is reflections from inside the link, mainly from connectors.
Figure 2-11 shows a typical return loss test result from a cable analyzer where the bottom curve is the limit for return loss, ending at 250MHz because Category 6 was selected for the test, and the irregular top line is the measured result for this test. The cursor is positioned at the frequency where the worst-case margin was detected. When a reported margin is positive, it indicates that the worst-case return loss is better than the limit (passed), whereas a negative margin indicates that the result exceeds the limit (failed). The cable analyzer also shows the wire pair and frequency where the worst-case return loss margin was measured.
Figure 2-11 Fluke Networks DTX-1800 return loss test results. The flat line below the irregular test result is the limit line for passing this test.
Near-End Crosstalk (NEXT)
When it comes to overall twisted-pair link operation, crosstalk has the greatest effect on link performance. Crosstalk is the undesirable signal transmission from one wire pair to another nearby pair (see Figure 2-12). Unwanted crosstalk signals generally result from capacitive and inductive coupling between adjacent pairs. Crosstalk increases at higher frequencies and is very destructive to data signaling. Most low-speed LAN protocols need two pairs of twisted-pair cable, one pair for each direction of traffic. Higher-speed LAN protocols typically need multiple pairs, and typically operate simultaneously in both directions on each twisted pair.
Figure 2-12 Crosstalk is a measure of how much of the transmitted signal "leaks" onto an adjacent wire pair
Test devices measure crosstalk by applying a test signal to one wire pair and measuring the amplitude of the crosstalk signals received by other wire pairs. Near-end crosstalk (NEXT) is computed as the ratio in amplitude (in volts) between the test signal transmitted and the crosstalk signal received when measured from the same end of the link. This ratio is generally expressed in decibels (dB). Higher NEXT values (smaller received crosstalk signals) correspond to less crosstalk and better link performance. The NEXT test is also the most common method used to infer the presence of split pairs in twisted-pair links.
Although crosstalk is a critical performance factor for twisted-pair links, it is also difficult to measure accurately, especially at lower frequencies where many of the common LAN protocols operate. TIA/EIA-568-B specifies that NEXT must be measured at increments or intervals not greater than the maximum frequency step size increments shown in Table 2-5. For improved accuracy, a smaller step size is better, although this may take longer to measure. A Category 3 link needs to be tested to 16 MHz and a Category 5e link to 100MHz, because those are their maximum frequency ratings.
Table 2-5. Maximum frequency step sizes allowed for compliance with TIA/EIA-568-B
Maximum Allowed Step Size
1 to 31.25MHz
150kHz (or 0.15MHz)
31.25 to 100MHz
250kHz (or 0.25MHz)
100 to 250MHz
500kHz (or 0.5MHz)
250 to 500MHz
NEXT loss must be measured from every pair to every other pair in a twisted-pair link, and from both ends of the link. This equates to 12 pair combinations for the typical four-pair cabling link. To shorten test times, some older field testers allowed the user to test the NEXT performance of a link by using larger frequency step sizes. The resulting distance between measurements does not comply with TIA/EIA-568-B, and may overlook link crosstalk faults.
All signals transmitted through a link are affected by attenuation. The farther the signal travels, the smaller it becomes. Because of attenuation, crosstalk occurring farther down the link contributes less to NEXT than crosstalk occurring at the near end of the link (refer to Figure 2-12). If the signal that is crossing to another pair is smaller, the amount that is available to cross is correspondingly smaller too. Furthermore, the coupled signal still has to travel back to the source end and is further attenuated as it returns. Thus, near-end crosstalk is worse closest to a transmission source where the signal is the largest (greatest amplitude) and the attenuation in the return path is the shortest. To verify proper link performance, you should measure NEXT from both ends of the link; this is also a requirement for complete compliance with all the high-speed cable specifications.
Crosstalk can be minimized by twisting wire pairs more, so that the signal coupling is "evened out." Twisted-pair wiring for LANs have more twists per unit length than telephone wiring. LANs use TIA/EIA Category 3 or better cable. Telephone wiring is typically comparable to the old UL Level 1 (see Table 2-1), and might not seem to be twisted at all. The higher the category, the more twists per unit length in the cable are necessary, and the higher the frequency rating will be. To ensure reliable LAN communications, cable pairs must not be left untwisted even for short distances. For this same reason, cables with parallel conductors (ribbon type or "silver satin" type cables) should never be used in LAN applications.
Signals from twisted-pair wiring may "leak" to the outside world and to other adjacent cables. The principle behind balanced twisted-pair cables is that, at every location along the cable, the voltage in one wire of a wire pair is equal in amplitude but opposite in phase to the voltage in the other wire of the wire pair. In addition to some other undesirable side effects, imbalance creates the effect of an antenna and receives external signals—thereby disrupting data with electromagnetic interference (EMI) and radio frequency interference (RFI). Substantial improvements have recently been made to cabling components—connectors in particular—which has had a positive impact because the majority of link problems occur at connectors, and the new connectors reduce these effects. To minimize the antenna effect, shielding the cable is a possible solution. When shielded cabling is used, however, a new set of potential problems is introduced, such as ground loops due to differences in the ground (earth) potential at opposite ends of the link. The ground-loop problem is often more serious than the EMI/RFI problem.
Generally, the problem of NEXT is worse in shielded cabling. The reason for this is that crimping the plugs to the shield of the cable enhances capacitive imbalance, one of the sources of NEXT. Also, shielded twisted-pair wiring is harder to install correctly, making it more prone to this sort of problem. Shielded twisted-pair cable comes in two basic types: 1) shielded twisted pair (STP), which has a foil shield around each individual pair and another shield around the four pairs, and 2) foil-screened twisted pair (FTP) or screened twisted pair (ScTP), which has a shield around the outside of the group of four pairs only, and is usually 100 ohm cabling. Some legacy cables could be either 120 ohm or 150 ohm cabling. With the advent of the 10GBASE-T application and the concerns over alien crosstalk, many manufacturers are promoting shielded or screened cable types. New terminology has been introduced to emphasize the cabling construction. The name F/UTP has been introduced to designate the foil around the four unshielded wire pairs. Proper grounding procedures must be followed when using these cable types. Screened cable types have been widely used in Europe because of strict laws intended to limit EMI/RFI emissions. As a side effect, they reduce external noise from interfering with the signals on the link. If proper balance is maintained, however, UTP cabling can provide EMI/RFI performance levels that also satisfy the European requirements.
Figure 2-13 shows typical NEXT test results. In both figures, the bottom curve is the TSB67 limit for NEXT and the top lines are the results for this test. When a reported margin is positive, this indicates that the worst-case NEXT is better than the limit, whereas a negative margin indicates that the results are worse than the limit. The cursor is positioned at the frequency where the worst-case margin was detected. The irregular shape of the top curve demonstrates that unless NEXT is measured at many points along the frequency range, low points (points of worse NEXT loss) could easily go undetected. Therefore, TIA/EIA-568-B defines a maximum frequency step size for NEXT measurements, as shown in Table 2-5.
Figure 2-13 Fluke DTX-1800 Near-end Crosstalk (NEXT) test results example. The left example shows the results for all pair combinations together. The right example shows only one pair combination. Each pair combination may be viewed separately. The cursor is at 8.8MHz, where the worst NEXT test result (smallest margin) was found.
If a NEXT failure is detected, it is possible to use other tests to pinpoint where along the length of the link the failure is occurring. One such test is called Time Domain Crosstalk (TDX), which is displayed in the same graphic format as a Time-Domain Reflectometry (TDR) test. The difference between TDR and TDX is that, in the case of a TDR, the signal is applied at one wire pair and the reflections are measured on the same wire pair. TDR reflections occur because of impedance anomalies. TDX applies a signal to one wire pair and measures the coupled signal on an adjacent wire pair.
Figure 2-14 shows two typical high-definition TDX test results. The vertical measurement spikes represent sources and magnitude of crosstalk. The vertical red lines are positioned at locations where the tester has determined the cable-under-test ends to be, and distance is shown at the bottom of the graph accordingly. The black vertical line is the user moveable cursor used to determine distance from the local tester end. The left graphic shows the point-source impact of a bad connection, either due to poor workmanship or poor connecting hardware. The right graphic shows crosstalk all along the cable-under test, which indicates that the cable itself is not good quality.
Figure 2-14 Fluke DTX-1800 HDTDX test result. Left screen shows connector problem, right screen shows poor quality cable. The test was made with the Permanent Link test adapter, so the cable under test begins 0.7m from the tester as indicated by the vertical red lines.
Attenuation-to-Crosstalk Ratio (ACR or ACRN)
ACR is calculated in an attempt to answer the question: While a transmission is taking place, how much does the noise from crosstalk disrupt the (attenuated) signal I am listening to? (See Figure 2-15.) ACR has been renamed ACRN (to indicate near-end crosstalk) in TIA/EIA-568-B.2-10 (the Augmented Category 6 standard), and is named ACR-N in the ISO 11801 standard.
Figure 2-15 ACR is calculated from attenuation and NEXT measurements
The attenuation-to-crosstalk ratio affects the bit-error rate (BER) directly and thereby the need for retransmissions. The noise consists of both externally induced noise and self-induced noise (which is NEXT). Self-induced noise usually dominates externally induced noise. The ACR is the same as the signal-to-noise ratio measurement when you deem that external noise is insignificant. The two factors considered in the calculation are NEXT and attenuation, as indicated in the name of the parameter. When insertion loss and NEXT loss measurements are expressed in dB, you can subtract the NEXT loss measurement from the insertion loss measurement to obtain the ratio. The closer the ACR result comes to zero dB, the less likely your link is going to work (see Figure 2-16).
Figure 2-16 ACRN Category 5e (TIA-568-B.2) and Category 6 (TIA-568-B.2-1) conformance
In Figure 2-16, the top graph is based on limit value calculations for a 100-meter Category 5e "channel" configuration specified in TIA/EIA-568-B.2, and the bottom graph shows the same calculation for Category 6 as specified in TIA/EIA-568-B.2-1. Category 5e and Category 6 only offer verified performance calculation formulas out to 100MHz and 250MHz, respectively. The formulas in the standard should not be extended beyond the specified frequency values. However, for the purpose of illustration the graph for Category 5e in Figure 2-18 has been extended beyond 100MHz using the Category 5e formulas. The graphs show calculated worst-case limits and plot three values: NEXT Loss, Insertion Loss (attenuation) and the derived ACR.
The limit for the ACRN value can also be viewed as the difference between the Insertion Loss and NEXT Loss limit lines in Figure 2-18.
In Figure 2-16, at the point where the plot lines for Insertion Loss and NEXT Loss intersect, the desired data signal will be exactly equal to the amount of noise contributed by NEXT at this frequency and the ACR limit value crosses the zero mark. Notice that the crosstalk will begin to be louder than the data signal at around 132MHz for Category 5e, and 226MHz for Category 6. To transfer data reliably, links used in LAN applications typically must perform at least 6dB better than the noise floor. For Category 6, the IEEE asked the TIA to extend the specification beyond the point where ACRN = 0 because of noise cancellation and error correction techniques it intended to apply to the appropriate Ethernet implementation.
This test is important for technologies such as 10BASE-T and 100BASE-TX, where only one pair is used in each direction. It does not mean as much for technologies that operate in parallel, such as 1000BASE-T, where power sum measurements are far more important.
In Figure 2-17, the bottom curved line is the Category 6 limit for NEXT, and the irregular stacked test results lines above are the per-pair results for this test. The cursor is positioned at the frequency where the worst-case margin was detected. When a reported margin is positive, this indicates that the worst-case ACRN is better than the limit, whereas a negative margin indicates that the result falls below the limit and the test fails. The cable analyzer permits results to be viewed for each cable pair combination separately.
Figure 2-17 DTX-1800 Category 6 ACRN test results example. The curve below the test results is the limit line for ACRN and extends to 250MHz as specified for Category 6.
Signal-to-Noise Ratio (SNR)
The signal-to-noise ratio is the combination of all disturbances generated within a cabling link plus the noise that penetrates the cable from external sources compared to the attenuated signal that transmits the information (see Figure 2-18). The internal disturbances that affect a wire pair within a cabling link consist of PSNEXT and PSACRF (both described later) contributed from the other three wire pairs in the cabling and return loss on the pair of interest. PSACRN and PSACRF calculate only a portion of the combined disturbance. No single test parameter has been defined that represents the true internal portion of the signal-to-noise ratio. With the advent of 10GBASE-T, the noise coupling from adjacent cabling links must be added to the SNR budget of every cabling link.
Figure 2-18 SNR is the same as ACRN plus external noise influences
An example of external noise might include the residual noise floor of the measuring instrument itself (for example, when you turn the volume on your music player equipment up very loud but don't press play—the hissing, crackly noise you hear is noise from the circuits themselves). The only problem with this measurement is being certain that you have included all the possible noise sources.
Advanced Frequency-Based Test Parameters Related to In-Channel and External Testing
The preceding test parameters were satisfactory for Ethernet implementations up through Fast Ethernet, as they were largely limited to low speed signaling (comparatively speaking) and the use of a single pair for transmit in each direction.
The parameters shown in Table 2-6 became necessary with the introduction of Gigabit Ethernet and higher signaling implementations. In these schemes, there are multiple pairs transmitting simultaneously in each direction, and therefore the effects of signals crossing over from adjacent wire pairs or from adjacent cables becomes significant.
Table 2-6. Measured and calculated test parameters
Measured Test Parameter
Calculated Test Parameter
Propagation Delay, Length
PSNEXT, ACRN, PSACRN
ANEXT, AFEXT (pair-to-pair)
ACRF (ELFEXT), PSACRF
More of the complex measurements are calculated rather than measured, unlike most of the simpler measurements previously described.
Far-End Crosstalk (FEXT)
The other kind of crosstalk is Far-End Crosstalk (FEXT). In this case, the signal coupled into the disturbed wire pair travels to the end of the link opposite the transmission source. In Figure 2-19, observe that any FEXT travels the same distance on an adjacent pair as the transmitted signal on the original pair. All crosstalk occurring as FEXT is subject to an amount of attenuation equal to the attenuation of the link, because it always travels the full distance of the link.
Figure 2-19 Far-end Crosstalk (FEXT)
Compare this with NEXT, which as discussed previously is attenuated in direct relation to the distance traveled to the point of coupling. The transmitted signal is attenuated on its way to the far end, and at any point that a portion of the signal crosses to an adjacent pair it must travel (and be attenuated) an equal distance before it arrives back at the source end.
The FEXT measurement compares the original signal to the signal coupled in an adjacent wire pair and arriving at the far end. NEXT is mostly a result of capacitive coupling along the cable, while FEXT is mostly the result of inductive coupling at connectors. For implementations that transmit on one pair in each direction, such as 10BASE-T and 100BASE-TX, FEXT is largely irrelevant. However, for technologies such as 1000BASE-T that transmit on multiple pairs in the same direction, FEXT is a very important property to test. FEXT represents another disturbance for a receiver. Consider the receiver at the right side of the bottom wire pair in Figure 2-19. This receiver is also affected by the NEXT from transmissions on the adjacent wire pair from right to left.
Because of attenuation, FEXT on longer cables is less than FEXT on shorter cables of the same type.
Attenuation to Crosstalk Ratio Far-End (ACRF)
Attenuation to Crosstalk Ratio Far-End (ACRF) is the ratio of FEXT to the attenuated signal over the affected wire pair (see Figure 2-20). Compare the FEXT disturbance to the attenuated signal arriving from the sender at the opposite end of the wire pair to assess the impact of the FEXT crosstalk on the signal transmission.
Figure 2-20 ACRF
This test parameter used to be called ELFEXT, or equal level far-end crosstalk, but is renamed as the test parameter ACRF (TIA) or ACR-F (ISO) in the new versions of the standards.
Like ACRN, ACRF represents a signal-to-noise ratio for the cabling. Higher ACRF values (in dB) mean that data signals received at the far end of the cabling are much larger than the far end crosstalk signals received. Higher ACRF values correspond to better cabling performance.
NEXT and FEXT coupling mechanisms tend to be similar in cable but can differ greatly in connecting hardware. Some connectors achieve good NEXT performance by balancing the inductive and capacitive currents that cause crosstalk. Because these currents are 180° out of phase at the near end of the cabling, they cancel out, which eliminates crosstalk at the near end. However, currents that cancel at the near end add up at the far end, causing far-end crosstalk and poor ACRF performance.
In Figure 2-20, a signal is transmitted on one wire pair. A signal transmitted on an adjacent pair crosses to the first wire pair, traveling in the same direction as the "good" signal. The FEXT electrons accompany the good signal electrons to the remote receive inputs of the LAN equipment. To properly decode the desired signal the amount of FEXT crosstalk must be smaller than the desired signal.
Power Sum Near-End Crosstalk (PSNEXT)
Power Sum NEXT loss is concerned with the combined effect of NEXT from all other pairs in the cable simultaneously. TIA/EIA standards use PSNEXT, whereas ISO standards use PS NEXT. Compare this with NEXT, where the amount of a transmitted signal from one pair is measured as crosstalk on one adjacent pair.
For each wire pair in the four-pair cable, PSNEXT loss is computed from three pair-to-pair NEXT loss test results (see Figure 2-21). Statistical theory indicates that a good assumption for the intensity of the total crosstalk in a link is a power sum. The value is calculated by taking the square root of the sum of the square of each crosstalk amplitude.
Figure 2-21 Power sum near-end crosstalk (PSNEXT)
For implementations that receive from only one pair in each direction, such as 10BASE-T and 100BASE-TX, PSNEXT is not relevant. However, for technologies such as 1000BASE-T that receive simultaneously from multiple pairs in the same direction, power sum measurements can be very important tests. The cumulative effect of crosstalk from multiple simultaneous transmission sources can be very detrimental to the signal you are trying to receive. In the case of 1000BASE-T, the requirements for pair-to-pair NEXT loss as specified are such that PSNEXT loss is always satisfied if the pair-to-pair NEXT loss requirements are satisfied, so PSNEXT calculations were not required. TIA/EIA-568-B certification requires this test.
Power Sum Attenuation to Crosstalk Ratio, Near-End (PSACRN)
Power Sum Attenuation to Crosstalk Ratio, Near-End (PSACRN) was previously called PSACR. The addition of Near-End was recently made to distinguish it from PSACRF for the far-end measurement. PSACRN values indicate how the amplitude of signals received from a far-end transmitter compares to the combined amplitudes of crosstalk produced by near-end transmissions on the other cable pairs. TIA/EIA standards use PSACRN, while ISO standards use PS ACR-N.
PSACRN is the difference (in dB) between each wire pair's attenuation (insertion loss) and the combined crosstalk received from the other pairs. Measured PSNEXT and Insertion Loss test results are used to calculate PSACRN values. Higher PSACRN values mean received signals are much larger than the crosstalk from all the other cable pairs. Higher PSACRN values correspond to better cabling performance.
Power Sum Attenuation to Crosstalk Ratio, Far-End (PSACRF)
Power Sum Attenuation to Crosstalk loss Ratio, Far-End (PSACRF) was previously defined as Power Sum Equal Level Far-End Crosstalk (PSELFEXT). PSACRF takes into account the combined crosstalk on a receive pair at the far end from signals transmitted simultaneously on the three adjacent pairs at the near end (see Figure 2-22). PSNEXT and PSACRN are for the near end; PSACRF is for the far end. TIA/EIA standards use PSACRF, whereas ISO standards use PS ACR-F.
Figure 2-22 Power Sum Attenuation to Crosstalk Ratio, Far-End (PSACRF)
The affect of attenuation, measured as insertion loss, is taken into account when the FEXT for the other three pairs in the link is calculated as a sum affecting the wire pair being measured. PSACRF results show how much the far end of each cable pair is affected by the combined farend crosstalk from the other pairs.
PSACRF is the difference (in dB) between the test signal and the crosstalk from the other pairs received at the far end of the link. PSACRF results are typically a few dB lower than worst-case FEXT results.
All the electronic influences thus far described have occurred within a single cable sheath. Alien crosstalk is any external influence, typically NEXT and FEXT, that is measured between adjacent cables. The influence does not project very far, and separation of between 1cm and 2cm reduces the influence to insignificant levels. Cable bundles and cable piled in conduit or cable trays is easily close enough together to suffer from this effect (see Figure 2-23). The effect is mitigated if the cable is placed loosely together so that no section of one cable is touching another cable for a significant distance. "Dressing" the cables for neatness by aligning them using cable ties and otherwise joining long runs together for extended distances causes alien crosstalk to increase.
Figure 2-23 Alien crosstalk is mostly a problem related to adjacent cables. This problem is exhibited whenever cables are in close proximity for any distance, such as a cable bundle between patch panels.
This crosstalk is worst between wire pairs with the same twist rate. The effect is greater for pairs with a lower twist rate. Impact increases with the distance over which the cables run in parallel, and with the frequency of the transmitted signals.
Alien crosstalk is also affected by "ambient noise" caused by RF signals (various radio communications or noise sources) and electromechanical disturbances. Noise from these other uncorrelated sources cannot be canceled out, and is included in alien crosstalk measurements.
Virtually all the previous frequency-based measurements are repeated for alien crosstalk, with the addition of some average values. A full suite of alien crosstalk measurements is made after all the in-channel measurements have been made (and pass). Then a cable in a given bundle is selected as the victim link (officially it is the disturbed link), and signals are transmitted on all adjacent links in the bundle called the disturber links. A complete test suite for a 48-cable bundle could take many hours because each cable must be the victim link in turn, and all disturber links must be used for each victim link. Because this extensive testing is simply too time-consuming, a process for sampling the most likely worst-case victim and disturber links has been laboratory validated. This process is a resource available from the Fluke Networks web site at www.flukenetworks.com/10gig in support of TIA TSB-155 testing.
Alien Near-End Crosstalk (ANEXT)
Alien Near-End Crosstalk loss (ANEXT) is the amount of unwanted signal coupling from a disturber pair in an adjacent cable measured on a victim pair in the measured cable. ANEXT is measured at the near end—the same end as the transmission source. In the same manner that NEXT is worst closest to the transmission source, ANEXT is worst nearest the adjacent transmission source.
Average Alien Near-End Crosstalk (Average ANEXT)
Average Alien Near-End Crosstalk (Average ANEXT) is the average amount of unwanted signal coupling at the near end measured for each of the four victim pairs in one victim cable at the near end.
Alien Far-End Crosstalk (AFEXT)
Alien Far-end Crosstalk loss (AFEXT) is the amount of unwanted signal coupling from a disturber pair in an adjacent cable measured on a victim pair in the disturbed (victim) cable. AFEXT is measured at the far end, the end away from the transmission source.
Attenuation to Alien Crosstalk Ratio Far-End (AACRF)
Attenuation to Alien Crosstalk Ratio Far-end (AACRF) is the difference (in dB) between the Alien FEXT from a disturber pair in an adjacent cable and the insertion loss of the victim pair in the disturbed cable at the far end.
Power Sum Alien Near-End Crosstalk (PSANEXT)
Power Sum Alien Near-End Crosstalk loss (PSANEXT) is the power sum of the unwanted crosstalk loss from adjacent disturber pairs in one or more adjacent disturber cables measured on a victim pair at the near end—the same end as the transmission source.
Power Sum Alien Far-End Crosstalk (PSAFEXT)
Power Sum Alien Far-End Crosstalk loss (PSAFEXT) is the power sum of the unwanted signal coupling from adjacent disturber pairs in one or more adjacent disturber cables measured on a victim pair at the far end—the end away from the transmission source.
Power Sum Attenuation to Alien Crosstalk Ratio Far-End (PSAACRF)
Power Sum Attenuation to Alien Crosstalk Ratio Far-End (PSAACRF) is the difference (in dB) between the Power Sum Alien Far End Crosstalk from multiple disturber pairs in one or more adjacent cables and the insertion loss of the victim pair in the measured cable at the far end.
Average Power Sum Attenuation to Alien Crosstalk Ratio Far-End (Average PSAACRF)
Average Power Sum Attenuation to Alien Crosstalk Ratio Far-End is the average of the Power Sum Attenuation to Alien Crosstalk Ratio Far End (Average PSAACRF) measurements for the four pairs in the victim cable.
The alien crosstalk evaluation of a disturbed or victim link requires that the PSANEXT and PSAACRF test parameters pass for all its wire pairs and the average of these four pairs after including the contribution by all disturber links. The disturber links must include all links bundled in the same bundle as the victim link, and links terminated in adjacent jacks in the panel if not already included because they are also part of the bundle.
Other Commonly Referenced Test Parameters
These next four test parameters are interesting, but are not usually part of a cable certification test. The problems related to these parameters are easily detected by other tests.
The TIA/EIA-568-B standard does not list capacitance as a required test for an installed link. To further support this, section 4 of TIA/EIA-568-B-2 states, "Mutual capacitance recommendations are provided for engineering design purposes" in several locations. If mutual capacitance is out of specification, characteristic impedance, return loss, and/or NEXT are directly affected, and field testing detects the problem accordingly with these tests.
From a troubleshooting perspective (not an engineering perspective), the goal of testing for capacitance problems is to identify the location of a link or installation fault. Rather than actually testing capacitance, it is far simpler and more accurate to use a TDR test to find the location of this sort of problem. Capacitance is also one of the test technologies used to infer the presence of split pairs in a twisted-pair cable.
When a high-frequency electrical signal is applied to a cable, the signal source experiences impedance. Impedance is a type of resistance that opposes the flow of alternating current (AC)—and network data is a type of high-frequency AC. A cable's characteristic impedance is a complex property, resulting from the combined effects of the cable's inductive, capacitive, and resistive values. These values are determined by physical parameters such as the size of the conductors, the distance between conductors, and the properties of the cable's insulation material.
Proper network operation depends on a constant characteristic impedance throughout the system's cables and connectors. Abrupt changes in characteristic impedance (called impedance discontinuities or impedance anomalies) cause signal reflections. Such changes in characteristic impedance can cause a high incidence of bit errors, as discussed previously.
The impact of characteristic impedance problems are more practically represented by the effect called return loss (see the description of return loss). Return loss tells you directly how bad the total effect of all reflections is.
Termination impedance present at the link ends must be equal to the characteristic impedance. Frequently, this termination impedance is included in the interface of equipment to be connected to the LAN. A good match between characteristic impedance and termination impedance provides for a good transfer of power to and from the link and minimizes reflections.
Complex high-speed LAN encoding methods, such as the 4D-PAM5 scheme used with 1000BASE-T, are even more sensitive to changes in characteristic impedance. The faster and more complex the signaling, the more sensitive the scheme is to this sort of problem. Lengths of untwisted wires must be kept to the absolute minimum, and lengths of cable with different characteristic impedance should never be mixed. If the characteristic impedance suddenly changes as a signal travels along a link, a reflection occurs that causes the signal (or a portion thereof) to bounce back toward the source. Such a reflected signal may again bounce back at another impedance anomaly and continue along the path of the originally transmitted signal. This combination of possible reflections may cause problems for the receiver (it creates signal jitter).
The characteristic impedance is almost always disturbed at connections or terminations. A LAN can tolerate some disturbance. However, it is critically important for the installer to untwist a twisted-pair cable to the minimum extent possible, particularly when installing links for high-speed LANs. In fact, for Category 5e cable, a link is permitted to have a maximum of 13 millimeters (0.5 inches) of untwisted wire at each termination point (TIA/EIA-568-B-1, paragraph 10.2.3). Installing an older or unrated RJ45 coupler to connect two cables normally exceeds this limit. Older RJ45 couplers often have particularly bad NEXT performance, and unless they are clearly marked with Category 5e or better ratings they should never be used in a Category 5e or better installation (the effect of poor quality couplers is shown in Figure 2-24). Rated couplers are typically larger than older poor quality couplers, and are much more expensive.
Figure 2-24 DTX 1800 HDTDX test results for two 5-meter (15 ft) Category 6 patch cables joined with an RJ45 coupler. The top graphic depicts the link with an older (unrated) RJ45 coupler, the middle has a Category 5 coupler, and the bottom has a Category 5e coupler.
Reflected signals are attenuated as they travel back, so the effect of reflections is reduced as the distance from the receiver increases. Sharp bends or kinks in LAN cable can also alter the cable's characteristic impedance. Poor electrical contacts, improper cable terminations, improper cable pairing, mismatched cable types (cables with different characteristic impedance values), and manufacturing defects in the cable all cause impedance discontinuities, resulting in degraded link performance.
An impedance measurement is sometimes used to infer the presence of split pairs in twisted-pair cable. When there is a split pair, the characteristic impedance measurement usually exhibits significantly different impedances for the pairs that were split.
Noise problems on a LAN link include impulse noise and continuous wideband noise. Noise does not include signals from other wire pairs, which are measured as forms of crosstalk.
Impulse noise is measured by counting the number of voltage spikes that exceed a certain threshold. A low impulse count is desirable for good network performance. However, an impulse noise test is not always sensitive enough for LANs that use higher levels of encoding than the common 10BASE-T networks. Wideband noise is a continuous presence of noise over a wide frequency band; it is not a part of the data transmission signal but potentially corrupts this signal. The lower the wideband noise voltage, the better the LAN performance will be. To resolve problems related to noise, it might be necessary to use other categories of tools, such as high-speed digitizing sampling oscilloscopes and spectrum analyzers with variable measurement bandwidths.
As mentioned during the discussion of NEXT, due to imbalance, LAN links also act as antennas. They can pick up noise signals from fluorescent lights, electric motors, photocopiers, and other similar devices that are located in proximity to the LAN cable. Also, when a transmitter of a radio or TV station is in the vicinity, significant noise can be picked up by the cable. Remember that the lower FM and TV bands are within the 1MHz to 100MHz range at which nearly all LAN protocols operate. Be sure to consider these external noise signal influences when you are planning your installation and route links as far away as possible or use shielded cable.
The LAN is a wideband system, meaning that all frequencies between 1MHz and 100MHz for Category 5e, or up to as high as 500MHz for Category 6A, make up the signal that is to be transmitted.
The DC loop resistance test is a basic resistance test used to detect the presence of termination resistor(s) on coax cable and to detect poor-quality connections on twisted-pair links.
A simple coax resistance test should show one of three expected results for Ethernet: open (no termination present), 50 ohms (one terminator present), or 25 ohms (two terminators present, one at each end of the cable). For RG-59 used with WAN links and wireless the measurements would reveal 75 ohms, or 37.5 ohms. If the test result deviates much from one of those three options, a cable fault is likely. 802.3 Ethernet specifies that termination resistors shall be 50 ohms with variations of only ±1 percent. However, the network usually continues to operate with variations of up to several ohms, although this introduces reflections of the data and reduces the effective maximum link length accordingly.
If the center conductor is shorted to the shield at the far end, thick coax should measure around 5 ohms at 500 meters, and thin coax should measure around 2 ohms at 185 meters (maximum lengths for Ethernet). If there are poor-quality connections along the path, each additional poor connection adds some amount of resistance. Similar tests may be made for RG-59.
For UTP, the DC loop resistance test is more significantly affected by link length. A typical DC loop resistance test on a 100-meter cable should provide results in the range of 9 ohms to 12 ohms. The TIA/EIA-568-B maximum limit is 9.38 ohms of resistance per 100 meters of UTP (at 20°C). The test on twisted pair is performed by shorting the two wires from a twisted pair together at the far end, and then measuring the resistance of the entire wire path. The quickest way to tell whether there is a problem is to compare the results from all four pairs. If one pair shows 25 ohms, and the other three are between 11 ohms and 14 ohms, it is highly probable that the 25 ohms pair has a link fault. The TIA/EIA-568-B limit for ScTP is 14 ohms per 100 meters (at 20°C).
Any problems with DC resistance show up as attenuation problems as well; therefore, DC resistance is not very important for field testing. Note that the TIA/EIA standards do not include the DC resistance test, whereas the ISO 11801 standard includes this as a pass/fail test. When deploying Power over Ethernet (PoE), it might be advisable to take note of the DC measurement results. An excessive resistance gives rise to heat and a greater than expected voltage drop.
A horizontal cable run consists of up to 90 meters of solid conductor cable, plus not more than 10 meters of stranded conductor patch cables in the equipment room, the user's work area, and any intermediate cross-connect or consolidation points.
The basic link was obsoleted by TIA/EIA-568-B when it superseded the TIA/EIA-568-A edition of that standard. The basic link was used by installers for testing the cable "in the wall" before the network was deployed, and often before power was available in new construction. The test required better performance than the channel link because there would be additional patch cables added later.
The basic link configuration does not permit any extra connectors in the tested link, but the point of measurement starts near the field tester and ends near the field tester remote unit at the other end of the link (see Figure 2-25). Therefore, the cable that is part of the basic link adapter is included in the test results each time.
Figure 2-25 Obsolete basic link test configuration
The permanent link replaces the basic link in TIA/EIA-568-B. The test is still used primarily by installers for testing the cable "in the wall," before the network is deployed.
The permanent link excludes the cable portions of the test adapters but includes the mated connection at each end (see Figure 2-26). The permanent link also allows for a consolidation point, which is desirable for open office cabling installations, and therefore more practical.
Figure 2-26 Permanent link test configuration
The significant difference between the basic and permanent link configurations is that the reference point for the measurements was moved from the tester interface to the plug end of the test adapter cable. This new test definition requires field testers to remove or subtract all measured effects of the test cord from each test result, but the mated connection with the link jacks is still included in the test results. From an installer's perspective, the change from basic to permanent link also means a loss of approximately 2dB of NEXT margin at 250MHz, which can lead to more failures and marginal results on Category 6/Class E links.
The channel link test is intended for the complete end-to-end or point-to-point cable path between two network devices, including the actual patch cables that will be used (see Figure 2-27). If a single common set of patch cables is used with the tester for each successive link tested instead of the end user's patch cables, the test does not comply with the requirements.
Figure 2-27 Channel link test configuration
Patch cords can make a significant difference, particularly because of a different mating of plugs and jacks (the cable of a patch cord rarely has much of an impact unless it is severely damaged, and that is usually quite evident and detectable by a visual inspection). The end user wants the performance of the complete cabling link verified, which must include the end user's patch cables and not the instrumentation patch cables. The tested patch cable used in the channel test must be left as part of the tested link. Changing patch cables invalidates the test results, and would require a retest to recertify.
The channel configuration may include the optional consolidation point as well as a cross-connect. Often there is just a patch panel in the equipment room. The connection at the tester end is not included in the test results.
The permanent link test offers an important advantage to the network owner. Patch cords may be changed a number of times during the life of the cabling installation. A passing permanent link test ensures that adding "good" patch cords automatically provides a passing channel. This advantage can be claimed only if two important conditions are met:
- The RJ45 plug at the end of the tester permanent link adapter is a test reference plug—a plug that operates in the very center of the plug specification range for all frequency-dependent parameters. The performance requirements of the centered test (reference) plug are defined in the TIA Category 6 and Category 6A standards. Typical commercial patch cords seldom if ever meet this stringent requirement and should not be used to perform the permanent link test. The test reference plug at the end of the permanent link test adapter guarantees that the jack meets the category specification.
- The patch cords you use to complete the channel must meet the category rating of the permanent link or better. You should either purchase patch cords for the high-performance links (Category 5e/Class D or above) from reputable manufacturers, or test patch cords with the proper adapters and against the appropriate standard to confirm their performance. Some manufacturers include the test results data with their patch cords to confirm their compliance with the standards. Be sure that a patch cord test was performed (for short cables), and not a channel test for up to 100 meters.